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U211B2/ B3
Phase Control Circuit - General Purpose Feedback
Description
The integrated circuit U211B2/ B3 is designed as a phase control circuit in bipolar technology with an internal frequency-voltage converter. Furthermore, it has an internal control amplifier which means it can be used for speedregulated motor applications. It has an integrated load limitation, tacho monitoring and soft-start functions, etc. to realize sophisticated motor control systems.
Features
D D D D D D
Internal frequency-to-voltage converter Externally-controlled integrated amplifier Overload limitation with a "fold back" characteristic Optimized soft-start function Tacho monitoring for shorted and open loop Automatic retriggering switchable 17(16) 1(1)
D D D D D
Triggering pulse typ. 155 mA Voltage and current synchronization Internal supply-voltage monitoring Temperature reference source Current requirement 3 mA DIP18 - U211B2, SO16 - U211B3
Package:
5*) Automatic retriggering Output pulse 4(4)
Voltage / Current detector
11(10) + 10(9) -
Control amplifier
6(5) 7(6)
Phase control unit o = f (V12)
3(3) Supply voltage limitation Reference voltage Voltage monitoring 2(2)
-V S GND
14(13) 15(14) Load limitation speed / time controlled
16(15)
controlled current sink -VRef 12(11)
Soft start
Frequencyto-voltage converter 9(8) 8(7)
Pulse-blocking tacho monitoring
18*)
13(12)
95 10360
Figure 1. Block diagram (Pins in brackets refer to SO16) *) Pins 5 and 18 connected internally
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
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U211B2/ B3
2 (20)
1N4007 D1 R1 M L 18 kW 2W R3 220 kW R4 470 kW 1 Automatic retriggering Output pulse 180 W 6 7 10 - 3 R2 1 MW R8 33 mW 1W 3.3 nF C2 2 -V S C1 GND C 11 Reference voltage Voltage monitoring 16 4 R 12 TIC 226 5 17 Voltage / Current detector 11 + Control amplifier VM = 230 V ~
47 k W
R13
R 31 100 kW
Set speed voltage
R14 56 k W
R19 100 kW
C 10
2.2 mF /16V
R 10 1 kW 14 Load limitation speed / time controlled 15
Phase control unit o = f (V12 )
Supply voltage limitation
2.2 mF
22 mF 25 V
N
1 MW R 9
C9 controlled current sink Soft start -V Ref 12 R11 2 MW C6 100 nF 22 k W R6 100 kW 10 mF /16V R7 C7 C8 220 nF C3 C5 1 nF 2.2 mF 16 V 13 9
Figure 2. Speed control, automatic retriggering, load limiting, soft start Frequency to voltage converter 8 220 nF C4 1 kW Speed sensor R5
95 10361
4.7mF /16V
Pulse blocking tacho 18 monitoring
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
Actual speed voltage
U211B2/ B3
Description
Mains Supply
The U211B2 is fitted with voltage limiting and can therefore be supplied directly from the mains. The supply voltage between Pin 2 (+ pol/ ) and Pin 3 builds up across D1 and R1 and is smoothed by C1. The value of the series resistance can be approximated using (see figure 2): R1 When the potential on Pin 7 reaches the nominal value predetermined at Pin 12, then a trigger pulse is generated whose width tp is determined by the value of C2 (the value of C2 and hence the pulse width can be evaluated by assuming 8 ms/nF). At the same time, a latch is set, so that as long as the automatic retriggering has not been activated, then no more pulses can be generated in that half cycle. The current sensor on Pin 1 ensures that, for operations with inductive loads, no pulse will be generated in a new half-cycle as long as a current from the previous half cycle is still flowing in the opposite direction to the supply voltage at that instant. This makes sure that "gaps" in the load current are prevented. The control signal on Pin 12 can be in the range 0 V to -7 V (reference point Pin 2). If V12 = -7 V then the phase angle is at maximum = amax i.e., the current flow angle is a minimum. The phase angle amin is minimum when V12 = V2.
+ V 2 -I V
M S
S
Further information regarding the design of the mains supply can be found in the data sheets in the appendix. The reference voltage source on Pin 16 of typ. -8.9 V is derived from the supply voltage and is used for regulation. Operation using an externally stabilised DC voltage is not recommended. If the supply cannot be taken directly from the mains because the power dissipation in R1 would be too large, then the circuit shown in the following figure 3 should be used. ~
Voltage Monitoring
24 V~
1 2 3 4 5
R1
C1
95 10362
As the voltage is built up, uncontrolled output pulses are avoided by internal voltage surveillance. At the same time, all of the latches in the circuit (phase control, load limit regulation, soft start) are reset and the soft-start capacitor is short circuited. Used with a switching hysteresis of 300 mV, this system guarantees defined start-up behavior each time the supply voltage is switched on or after short interruptions of the mains supply.
Figure 3. Supply voltage for high current requirements
Phase Control
There is a general explanation in the data sheet, TEA1007, on the common phase control function. The phase angle of the trigger pulse is derived by comparing the ramp voltage (which is mains synchronized by the voltage detector) with the set value on the control input Pin 12. The slope of the ramp is determined by C2 and its charging current. The charging current can be varied using R2 on Pin 6. The maximum phase angle amax can also be adjusted using R2.
Soft-Start
As soon as the supply voltage builds up (t1), the integrated soft-start is initiated. The figure below shows the behaviour of the voltage across the soft-start capacitor and is identical with the voltage on the phase control input on Pin 12. This behaviour guarantees a gentle start-up for the motor and automatically ensures the optimum run-up time.
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U211B2/ B3
95 10272
VC3 V12
The converter is based on the charge pumping principle. With each negative half wave of the input signal, a quantity of charge determined by C5 is internally amplified and then integrated by C6 at the converter output on Pin 10. The conversion constant is determined by C5, its charge transfer voltage of Vch, R6 (Pin 10) and the internally adjusted charge transfer gain. Gi I 10 I9
V0
+ 8.3
C5 R6 Vch
k = Gi
t1 t2 ttot t3 t
The analog output voltage is given by VO = k
@f
Figure 4. Soft-start
t1 t2 t1 + t2 t3 ttot
= build-up of supply voltage = charging of C3 to starting voltage = dead time = run-up time = total start-up time to required speed
C3 is first charged up to the starting voltage V0 with typical 45 mA current (t2). By then reducing the charging current to approx. 4 mA, the slope of the charging function is substantially reduced so that the rotational speed of the motor only slowly increases. The charging current then increases as the voltage across C3 increases giving a progressively rising charging function which accelerates the motor more and more strongly with increasing rotational speed. The charging function determines the acceleration up to the set-point. The charging current can have a maximum value of 55 mA.
The values of C5 and C6 must be such that for the highest possible input frequency, the maximum output voltage VO does not exceed 6 V. While C5 is charging up, the Ri on Pin 9 is .approx. 6.7 kW. To obtain good linearity of the f/V converter the time constant resulting from Ri and C5 should be considerably less (1/5) than the time span of the negative half-cycle for the highest possible input frequency. The amount of remaining ripple on the output voltage on Pin 10 is dependent on C5, C6 and the internal charge amplification. VO = Gi Vch C6 C5
The ripple Vo can be reduced by using larger values of C6. However, the increasing speed will then also be reduced. The value of this capacitor should be chosen to fit the particular control loop where it is going to be used.
Frequency to Voltage Converter
The internal frequency to voltage converter (f/Vconverter) generates a DC signal on Pin 10 which is proportional to the rotational speed using an AC signal from a tacho-generator or a light beam whose frequency is in turn dependent on the rotational speed. The high impedance input Pin 8, compares the tacho-voltage to a switch-on threshold of typ. -100 mV. The switch-off threshold is given with -50 mV. The hysteresis guarantees very reliable operation even when relatively simple tacho-generators are used. The tacho-frequency is given by: f where: n + 60 p (Hz)
Pulse Blocking
The output of pulses can be blocked using Pin 18 (standby operation) and the system reset via the voltage monitor if V18 -1.25 V. After cycling through the switching point hysteresis, the output is released when V18 -1.5 V followed by a soft-start such as that after turn on. Monitoring of the rotation can be carried out by connecting an RC network to Pin 18. In the event of a short or open circuit, the triac triggering pulses are cut off by the time delay which is determined by R and C. The capacitor C is discharged via an internal resistance Ri = 2 kW with each charge transfer process of the f/V converter. If there are no more charge transfer processes C is charged up via R until the switch-off threshold is exceeded and the triac triggering pulses are cut off. For operation without trigger pulse blocking or monitoring of the rotation, Pins 18 and 16 must be connected together.
n = revolutions per minute p = number of pulses per revolution
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U211B2/ B3
C = 1 mF 10 V 18 17 16 15 (reference voltage Pin 16) then a latch is set and the load limiting is turned on. A current source (sink) controlled by the control voltage on Pin 15 now draws current from Pin 12 and lowers the control voltage on Pin 12 so that the phase angle a is increased to amax. The simultaneous reduction of the phase angle during which current flows causes firstly: a reduction of the rotational speed of the motor which can even drop to zero if the angular momentum of the motor is excessively large, and secondly: a reduction of the potential on C9 which in turn reduces the influence of the current sink on Pin 12. The control voltage can then increase again and bring down the phase angle. This cycle of action sets up a "balanced condition" between the "current integral" on Pin 15 and the control voltage on Pin 12. Apart from the amplitude of the load current and the time during which current flows, the potential on Pin 12 and hence the rotational speed also affects the function of the load limiting. A current proportional to the potential on Pin 10 gives rise to a voltage drop across R10, via Pin 14, so that the current measured on Pin 14 is smaller than the actual current through R8. This means that higher rotational speeds and higher current amplitudes lead to the same current integral. Therefore, at higher speeds, the power dissipation must be greater than that at lower speeds before the internal threshold voltage on Pin 15 is exceeded. The effect of speed on the maximum power is determined by the resistor R10 and can therefore be adjusted to suit each individual application. If, after the load limiting has been turned on, the momentum of the load sinks below the "o-momentum" set using R10, then V15 will be reduced. V12 can then increase again so that the phase angle is reduced. A smaller phase angel corresponds to a larger momentum of the motor and hence the motor runs up - as long as this is allowed by the load momentum. For an already rotating machine, the effect of rotation on the measured "current integral" ensures that the power dissipation is able to increase with the rotational speed. the result is: a current controlled accelleration run-up., which ends in a small peak of accelleraton when the set point is reached. The latch of the load limiting is simultaneously reset. The speed of the motor is then again under control and it is capable of carrying its full load. The above mentioned peak of accelleration depends upon the ripple of actual speed voltage. A large amount of ripple also leads to a large peak of accelleration. The measuring resistor R8 should have a value which ensures that the amplitude of the voltage across it does not exceed 600 mV.
R = 1 MW
1
2
3
4
95 10363
Figure 5. Operation delay
Control Amplifier (Figure 2)
The integrated control amplifier with differential input compares the set value (Pin 11) with the instantaneous value on Pin 10 and generates a regulating voltage on the output Pin 12 (together with the external circuitry on Pin 12) which always tries to hold the actual voltage at the value of the set voltages. The amplifier has a transmittance of typically 1000 mA/V and a bipolar current source output on Pin 12 which operates with typically 110 mA. The amplification and frequency response are determined by R7, C7, C8 and R11 (can be left out). For open loop operation, C4, C5, R6, R7, C7, C8 and R11 can be omitted. Pin 10 should be connected with Pin 12 and Pin 8 with Pin 2. The phase angle of the triggering pulse can be adjusted using the voltage on Pin 11. An internal limitation circuit prevents the voltage on Pin 12 from becoming more negative than V16 + 1 V.
Load Limitation
The load limitation, with standard circuitry, provides absolute protection against overloading of the motor. the function of the load limiting takes account of the fact that motors operating at higher speeds can safely withstand large power dissipations than at lower speeds due to the increased action of the cooling fan. Similary, considerations have been made for short term overloads for the motor which are, in practice, often required. These finctions are not damaging and can be tolerated. In each positive half-cycle, the circuit measures via R10 the load current on Pin 14 as a potential drop across R8 and produces a current proportional to the voltage on Pin 14. This current is available on Pin 15 and is integrated by C9. If, following high current amplitudes or a large phase angle for current flow, the voltage on C9 exceeds an internally set threshold of approx. 7.3 V
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
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U211B2/ B3
Design Hints
Practical trials are normally needed for the exact determination of the values of the relevant components in the load limiting. To make this evaluation easier, the Parameters Pmax Pmin Pmax / min td tr Pmax Pmin td tr n.e R10 increases increases increases n.e. n.e. following table shows the effect of the circuitry on the important parameters of the load limiting and summarises the general tendencies. Component affected R9 decreases decreases n.e. decreases increases C9 n.e. n.e. n.e. increases increases
- maximum continuous power dissipation - power dissipation with no rotation - operation delay time - recovery time - no effect
P1 = f(n) n 0 P1 = f(n) n = 0
0
Pulse Output Stage
The pulse output stage is short circuit protected and can typically deliver currents of 125 mA. For the design of smaller triggering currents, the function IGT = f(RGT) has been given in the data sheets in the appendix.
General Hints and Explanation of Terms
To ensure safe and trouble-free operation, the following points should be taken into consideration when circuits are being constructed or in the design of printed circuit boards. - The connecting lines from C2 to Pin 7 and Pin 2 should be as short as possible: The connection to Pin 2 should not carry any additional high current such as the load current. When selecting C2, a low temperature coefficient is desirable. - The common (earth) connections of the set-point generator, the tacho-generator and the final interference suppression capacitor C4 of the f/V converter should not carry load current. - The tacho-generator should be mounted without influence by strong stray fields from the motor. - The connections from R10 and C5 should be as short as possible. To achieve a high noise immunity, a maximum ramp voltage of 6 V should be used. The typical resistance Ro can be calculated from Io as follows: T(ms) 1.13(V) 10 3 R o (kW) C nF) 6(V)
Automatic Retriggering
The variable automatic retriggering prevents half cycles without current flow, even if the triac is turned off earlier e.g. due to a collector which is not exactly centered (brush lifter) or in the event of unsuccessful triggering. If it is necessary, another triggering pulse is generated after a time lapse which is determined by the repetition rate set by resistance between Pin 5 and Pin 3 (R5-3). With the maximum repetition rate (Pin 5 directly connected to Pin 3), the next attempt to trigger comes after a pause of 4.5 tp and this is repeated until either the triac fires or the half-cycle finishes. If Pin 5 is connected, then only one trigger pulse per half-cycle is generated. Because the value of R5-3 determines the charging current of C2, any repetition rate set using R5-3 is only valid for a fixed value of C2.
+
T = Period duration for mains frequency (10 ms at 50 Hz) Co = Ramp capacitor, max. ramp voltage 6 V and constant voltage drop at Ro = 1.13 V. A 10% lower value of Ro (under worst case conditions) is recommended.
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U211B2/ B3
95 10716
V Mains Supply
p/2
p
3/2p
2p
VGT Trigger Pulse VL Load Voltage
tp
tpp = 4.5 tp
IL Load Current
o F
Figure 6. Explanation of terms in phase relationship
Design Calculations for Mains Supply
The following equations can be used for the evaluation of the series resistor R1 for worst case conditions: R 1max
+ 0.85 V + (V
Mmin
- V Smax 2 I tot
R 1min
+ V 2 -I V
M
Smin
Smax
P (R1max) where:
Mmax
- V Smin) 2 2 R1
= Mains voltage = Supply voltage on Pin 3 = Total DC current requirement of the circuit Itot = IS + Ip + Ix ISmax = Current requirement of the IC in mA Ip = Average current requirement of the triggering pulse = Current requirement of other peripheral components Ix R1 can be easily evaluated from the figures 20 to 22. VM
VS
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U211B2/ B3
Absolute Maximum Ratings
Reference point Pin 2, unless otherwise specified Parameters Current requirement t 10 ms Synchronization current t t f/V converter Input current t Load limiting Limiting current, neg. half wave t Input voltage Phase control Input voltage Input current Soft-start Input voltage Pulse output Reverse voltage Pulse blocking Input voltage Amplifier Input voltage Pin 9 open Reference voltage source Output current Storage temperature range Junction temperature Ambient temperature range Pin 3 Pin 1 Pin 17 Pin 1 Pin 17 Pin 8 Symbol -IS -is IsyncI IsyncV iI iI II iI Pin 14 II Pin 14 Pin 15 Pin 12 Pin 12 Pin 6 Pin 13 Pin 4 Pin 18 Pin 11 Pin 10 Pin 16 Vi -VI -VI II -II -VI VR -VI VI -VI Io Tstg Tj Tamb 5 35 1 V16 to 0 0 to 7 500 1 V16 to 0 VS to 5 V16 to 0 0 to VS V16 to 0 7.5 -40 to +125 125 -10 to +100 V mA Value 30 100 5 5 35 35 3 13 mA Unit mA
t 10 ms t 10 ms t 10 ms t 10 ms
mA
V
mA
mA V V V V
mA C C C
Thermal Resistance
Parameters Junction ambient DIP18 SO16 on p.c. SO16 on ceramic Symbol RthJA Maximum 120 180 100 Unit K/W
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U211B2/ B3
Electrical Characteristics
-VS = 13.0 V, Tamb = 25C, reference point Pin 2, unless otherwise specified Parameters Test Conditions / Pins Supply voltage for mains opPin 3 eration Supply voltage limitation -IS = 4 mA Pin 3 -IS = 30 mA DC current requirement -VS = 13.0 V Pin 3 Reference voltage source -IL = 10 mA Pin 16 -IL = 5 mA Temperature coefficient Pin 16 Voltage monitoring Turn-on threshold Pin 3 Turn-off threshold Pin 3 Phase control currents Synchronization current Pin 1 Voltage limitation Reference ramp, figure 7 Charge current Ro-reference voltage Temperature coefficient Pulse output, figure 18 Output pulse current Reverse current Output pulse width Amplifier Common mode signal range Input bias current Input offset voltage Output current Symbol -VS -VS -VS IS -VRef -TCVRef -VSON -VSOFF 11.2 9.9 0.35 0.35 1.4 1.6 Min. 13.0 14.6 14.7 1.2 8.6 8.3 Typ. Max. VLimit 16.6 16.8 3.0 9.2 9.1 Unit V V mA V mV/K V V 2.0 2.0 1.8 V mA
2.5 8.9 0.5 13.0 10.9
"I
Pin 17 L = 5 mA Pins 1 and 17
"I "I "V
syncI
syncV I
I7 = f (R6); Pin 7 R6 = 50 k to 1 MW a 180C Pins 6 and 3 Pin 6 Pin 4 RGT = 0, VGT = 1.2 V C = 10 nF Pins 10 and 11 Pin 11 Pins 10 and 11 Pin 12
I7 VoRef TCVoRef Io Ior tp V10, 11 IIO V10 -IO +IO Yf -VTON -VTOFF II RO
1 1.06
20 1.13 0.5 155 0.01 80
mA
1.18
V mV/K mA
mA ms
100
190 3.0
V16 0.01 10 110 120 1000 3.7 1.5 1.25 0.3 6
-1 1 145 165
V
mA
mV
mA
75 88
Short circuit forward, Figure 14 Pin 12 transmittance I12 = f(V10 -11) Pulse blocking, tacho-monitoring Pin 18 Logic-on Logic-off Input current V18 = VTOFF = 1.25 V V18 = V16 Output resistance
mA/V
V 1.0 1 10
mA
14.5 1.5
kW
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U211B2/ B3
Parameters Test Conditions / Pins Frequency to voltage converter Pin 8 Input bias current Input voltage limitation Figure 13 II = -1 mA II = +1 mA Turn-on threshold Turn-off threshold Charge amplifier Discharge current Figure 2 C5 = 1 nF, Pin 9 Charge transfer voltage Pins 9 to 16 Charge transfer gain I10/I9 Pins 9 and 10 Conversion factor Figure 2 C5 = 1 nF, R6 = 100 kW Output operating range Pins 10 to 16 Linearity Soft-start, figures 8, 9, 10, 11, 12 f/v-converter non-active Starting current V13 = V16, V8 = V2 Pin 13 Final current V13 = 0.5 Pin 13 f/v-converter active Starting current V13 = V16 Pin 13 Final current V13 = 0.5 Discharge current Restart pulse Pin 13 Automatic retriggering, figure 19 Pin 5 Repetition rate R5-3 = 0 p R5-3 = 15 kW Load limiting, figures 15, 16, 17 Pin 14 Operating voltage range Pin 14 Offset current V10 = V16 Pin 14 V14 = V2 via 1 kW Pin 15-16 Input current V10 = 4.5 V Pin 14 Output current V14 = 300 mV Pin 15-16 Overload ON Pin 15-16 Symbol IIB -VI +VI -VTON -VTOFF 660 7.25 20 100 50 Min. Typ. 0.6 Max. 2 750 8.05 150 Unit
mA
mV V mV mV
Idis Vch Gi K VO 6.50 7.5
0.5 6.70 8.3 5.5 0-6 6.90 9.0
mA V
1
45 85 4 55 3 4.5 20
mV/Hz V % 55 130 7 80 10 6
IO
20 50 2 30 0.5 3
mA m mA mA
mA tp
IO IO tpp
VI IO
-1.0 5 0.1 90 7.4
1.0 12 1.0 120 140 7.7
V
mA
V
II IO VTON
60 110 7.05
10 (20)
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U211B2/ B3
240 Phase Control Reference Point Pin 2 200 ( ) 10nF 160 4.7nF V13 ( V ) 2.2nF 6 8 Soft Start 10
Phase Angle
a
120 80 0 0 0.2 0.4 0.6 0.8 1.0
95 10305
4 C o/t=1.5nF 2 f/V-Converter Non Active Reference Point Pin 16 0 Ro ( MW ) t=f(C3)
95 10302
Figure 7.
100 Soft Start 80 I 13 ( mA ) V13 ( V ) 8 10 Soft Start
Figure 10.
f/V-Converter Active Reference Point Pin 16
60
6
40 20 f/V-Converter Non Active Reference Point Pin 16 0 0
95 10303
4 2 0 2 4 6 V13 ( V ) 8 10
95 10306
t=f(C3)
Figure 8.
100 Soft Start 80 V13 ( V ) f/V-Converter Active Reference Point Pin 16 I 13 ( mA ) 60 8 10 Soft Start
Figure 11.
95 10307
Reference Point Pin 16 6 4
40 2 20 0 0
95 10304
0 t=f(C3) Motor Standstill ( Dead Time ) Motor in Action
2
4
6 V13 ( V )
8
10
Figure 9.
Figure 12.
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
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U211B2/ B3
500 f/V-Converter 250 I 14-2 ( m A) I 8 (mA ) Reference Point Pin 2 0 150 200 Load Limit Control
100
-250
50
-500 -10
95 10308
0 -8 -6 -4 -2 0 2 4
95 10311
0
2
4 V10-16 (V)
6
8
V8 ( V )
Figure 13.
250 100 Control Amplifier 200 50 I 15-16 ( m A ) I 12 ( mA ) 150
Figure 16.
Load current detection
0
100 50 I15=f ( VShunt ) V10=V16
-50 Reference Point for I12 = -4V -200 -100 0 100 200 300
95 10312
-100
0 0 100 200 300 400 500 600 700 V10-11 ( V ) V14-2 ( mV )
-300
95 10309
Figure 14.
200 Load Limit Control 150 80 I GT ( mA ) 100
Figure 17.
Pulse Output
m A)
60
12-16 (
100
-I
40 20
1.4V
VGT=0.8V
50
0 0
95 10310
0 2 4 V15-16 ( V ) 6 8
95 10313
0
200
400
RGT ( W )
600
800
1000
Figure 15.
Figure 18.
12 (20)
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
U211B2/ B3
20 Automatic Retriggering 15 ( kW ) P(R1) ( W ) 4 3 2 5 1 0 0
95 10314
6 5 Mains Supply
R 5-3
10
0 6 12 tpp/tp 18 24 30
95 10316
0
10
20 R1 ( kW )
30
40
Figure 19.
50 6 5
Figure 21.
40 Mains Supply 30 P(R1) ( W ) R 1( kW )
Mains Supply 4 3 2 1 0 0 4 8 Itot ( mA ) 12 16
95 10317
20 10 0
0
3
6
9
12
15
95 10315
Itot ( mA )
Figure 20.
Figure 22.
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
13 (20)
U211B2/ B3
Set speed voltage 2.2 m F 10 V 250 kW R13 47 kW R31 R7 15 kW
100 nF
2.2 mF / 10 V
C10
C5
680 pF
R6
C6
C4
220 nF
C7
1 MW
220 nF
13
U211B2
6
2.2 mF 10 V
4.7m F 10 V
14
15
C9
4
5
16
R9 470 kW
3
17
10 kW
R14
2
GND
-VS
R2 1 MW
220 k W
2.2 m F
18 kW 1.5 W
470 kW
R3
C11
T2
R4
180 W
18
1
R12
C2 2.2 nF C /t
12
C8
C3
7
R
o
o
47 kW
1N4004
D1
R1
T1
R15
BZX55
47 kW
R16
C1
22 mF 25 V N R8= 3 x 11 mW 1W
95 10364
R10 2.2 kW
M
Figure 23. Speed control, automatic retriggering, load switch-off, soft start
The switch-off level at maximum load shows in principle the same speed dependency as the original version (see figure 2), but when reaching the maximum load, the motor is switched off completely.
This function is effected by the thyristor (formed by T1 and T2) which ignites when the voltage at Pin 15 reaches typ. 7.4 V (Reference point Pin 16). The circuit is thereby switched into the "stand-by" over the release Pin 18.
14 (20)
230 V~
L
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
Speed sensor
10
9
100 kW
R11
11
8
R5 1 kW
U211B2/ B3
Set speed voltage 2.2 m F 10 V R31 250 k W R13 47 k W R7 15 kW
100 nF
2.2 m F 10 V /
C10
R6
C6
680 pF
C4 220 nF
C7
C5
100 kW 220 nF
1 MW
13
U211B2
6
2.2 m F 10 V
4.7m F 10 V
14
15
C9
4
5
17
2
GND -VS
16
2.2 m F
C 11
3
R2 1 MW
R9 470 kW
R14 10 kW
220 k W
18 kW 1.5 W R4
470 kW
R3
180W
18
1
R12
C2 2.2 nF C
12
C8
C3
7
R
o
o
/t
33 kW
R15
T2
D1 1N4004
R1
T1
C1 230 V~ N R8 = 3 x 11 mW 1W
47 kW
R16
BZX55
95 10366
Figure 24. Speed control, automatic retriggering, load switch-off, soft-start
The maximum load regulation shows the principle in the same speed dependency as the original version (see figure 2). When reaching the maximum load, the control unit is turned to amax, adjustable with R2. Then only IO flows. This function is effected by the thyristor, formed by T1 and T2 which ignites as soon as the voltage at Pin 15 reaches ca. 6.8 V (Reference point Pin 16). The potential
L
R10 2.2 kW
at Pin 15 is lifted and kept by R14 over the internally operating threshold whereby the maximum load regulation starts and adjusts the control unit constantly to amax (IO), inspite of a reduced load current. The motor shows that the circuit is still in operation by a quiet buzzing noise.
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
M
22 m F 25 V
Speed sensor
10
9
R 11
11
8
R5 1 kW
15 (20)
U211B2/ B3
16 (20)
C 11 68 k W R6 C6 R11 C3 1.5 MW C7 1m F /10 V 2.2 m F /10 V 16 14 15 13 12 11 10 R 13 47 kW 100 nF R31 250 kW Set speed voltage 2.2 m F 10 V 1 MW 220 k W R3 18 17 C 10 22 nF C9 4.7m F C8 R9 1 M W 220 nF 2.2 m F 10 V D1 1N4004
95 10365
L
R10 1 kW
230 V~
U211B2
M R1 1 4 -VS R4 GND R12 220 W C1 22 m F 25 V Speed sensor 470 k W 2 3 5 18 kW 1.5 W 6 7 8 9 1 nF R2 1 MW C5 R
o
R7 22 k W
N
C2 2.2 nF C
R5 1 kW
o
/t
C4 220 nF
Figure 25. Speed control, automatic retriggering, load limiting, soft-start, tacho control
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
R8 = 3 x 11 mW 1W
R8 47 k W 220 nF 2.2 mF 10 V C3 R7 470 kW 10 mF C8 18 17 14 16 13 11 12 15 L1 1N4004 D1 10 C7 470 nF 10 V R11 16 k W C11 22 nF 220 kW R4
C4
4.7 mF 10 V C13
R18 Set speed min R31 100 kW
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
R13 Set speed max L2 R1 1 4 -VS R6 5 R5 GND 100 W 470 kW IGT = 50 mA C1 2 3 6 18 k W 1.5 W 7 8 C6 R2 1 MW R3 4.7 kW Ro C2 Co/t 3.3 nF R10 680 pF 9
all diodes BYW83
M
U211B2
CNY 70
230 V~
100 W
R14
C12 47 mF 25 V
R9
220 k W
150 nF 250 V~
C5 1.5 k W 470 nF 100 W R17 R16 470 W
Figure 26. Speed control with reflective opto coupler CNY70 as emitter
1N4004 ca 220 Pulses / Revolution D2 3.5 k W / 8 W R15 C10 100 mF 10 V Z3
BZX55 C9V1
U211B2/ B3
95 10687
17 (20)
U211B2/ B3
18 (20)
C9 C6 470 nF C10 R14 Set speed min R31 R9 220 k W C11 22 nF 10 mF C7 18 17 16 15 14 13 12 11 10 D1 1N4004 M R1 1 4 -VS 100 W R12 R2 1 MW R4 GND 220 k W IGT = 50 mA C1 2 3 5 6 7 10 k W 1.1 W 8 9 C5 Ro C2 Co/t 3.3 nF 680 pF 10 kW R16 R5 2.2 k W C4 1 nF 1mF C13 R17 C8 470 nF R11 820 k W 2.2 mF 10 V C3 220 k W 4.7 mF 10 V R6 82 k W 47 mF 10 V 110 kW R3 R7 16 kW R13 Set speed max
95 10688
R10 1.1 kW
230 V~
U211B2
CNY 70
150 nF 250 V~
100 W
C12
9V R18 33 k W
Figure 27. Speed control, max. load control with reflective opto coupler CNY70 as emitter
22 mF 25 V 470 W
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
R8= 3 x 0.1 W
U211B2/ B3
The circuit is designed as a speed control on the reflection-coupled principle with 4 periods per revolution and a max. speed of 30.000 rpm. The separation of the coupler from the rotating aperture should be 1 mm approximately. In this experimental circuit, the power supply for the coupler was provided externally because of the relatively high current consumption. Instructions for adjusting: D In the initial adjustment of the phase-control circuit, R2 should be adjusted so that when R14 = 0 and R31 are in min. position, the motor just turns. D The speed can now be adjusted as desired by means of R31 between the limits determined by R13 and R14. D The switch-off power of the limit load control can be set by R9. The lower R9, the higher the switch-off power.
Dimensions in mm
Package: DIP18 - U211B2
94 8877
Package: SO16 - U211B3
94 8875
TELEFUNKEN Semiconductors Rev. A1, 29-May-96
19 (20)
U211B2/ B3
Ozone Depleting Substances Policy Statement
It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to 1. Meet all present and future national and international statutory requirements. 2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances ( ODSs). The Montreal Protocol ( 1987) and its London Amendments ( 1990) intend to severely restrict the use of ODSs and forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these substances. TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of continuous improvements to eliminate the use of ODSs listed in the following documents. 1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively 2 . Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental Protection Agency ( EPA) in the USA 3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C ( transitional substances ) respectively. TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances.
We reserve the right to make changes to improve technical design and may do so without further notice. Parameters can vary in different applications. All operating parameters must be validated for each customer application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany Telephone: 49 ( 0 ) 7131 67 2831, Fax number: 49 ( 0 ) 7131 67 2423
20 (20)
TELEFUNKEN Semiconductors Rev. A1, 29-May-96

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